ZHCSB64A June   2013  – September 2014 SN6501-Q1


  1. 特性
  2. 应用范围
  3. 说明
  4. 修订历史记录
  5. Pin Configuration and Functions
  6. Specifications
    1. 6.1 Absolute Maximum Ratings
    2. 6.2 Handling Ratings
    3. 6.3 Recommended Operating Conditions
    4. 6.4 Thermal Information
    5. 6.5 Electrical Characteristics
    6. 6.6 Switching Characteristics
    7. 6.7 Typical Characteristics
  7. Parameter Measurement Information
  8. Detailed Description
    1. 8.1 Overview
    2. 8.2 Functional Block Diagram
    3. 8.3 Feature Description
      1. 8.3.1 Push-Pull Converter
      2. 8.3.2 Core Magnetization
    4. 8.4 Device Functional Modes
      1. 8.4.1 Start-Up Mode
      2. 8.4.2 Operating Mode
      3. 8.4.3 Off-Mode
  9. Application and Implementation
    1. 9.1 Application Information
    2. 9.2 Typical Application
      1. 9.2.1 Design Requirements
      2. 9.2.2 Detailed Design Procedure
        1. SN6501 Drive Capability
        2. LDO Selection
        3. Diode Selection
        4. Capacitor Selection
        5. Transformer Selection
          1. V-t Product Calculation
          2. Turns Ratio Estimate
          3. Recommended Transformers
      3. 9.2.3 Application Curve
      4. 9.2.4 Higher Output Voltage Designs
      5. 9.2.5 Application Circuits
  10. 10Power Supply Recommendations
  11. 11Layout
    1. 11.1 Layout Guidelines
    2. 11.2 Layout Example
  12. 12器件和文档支持
    1. 12.1 器件支持
      1. 12.1.1 第三方产品免责声明
    2. 12.2 商标
    3. 12.3 静电放电警告
    4. 12.4 术语表
  13. 13机械封装和可订购信息


机械数据 (封装 | 引脚)
散热焊盘机械数据 (封装 | 引脚)

9 Application and Implementation


Information in the following applications sections is not part of the TI component specification, and TI does not warrant its accuracy or completeness. TI’s customers are responsible for determining suitability of components for their purposes. Customers should validate and test their design implementation to confirm system functionality.

9.1 Application Information

The SN6501-Q1 is a transformer driver designed for low-cost, small form-factor, isolated DC-DC converters utilizing the push-pull topology. The device includes an oscillator that feeds a gate-drive circuit. The gate-drive, comprising a frequency divider and a break-before-make (BBM) logic, provides two complementary output signals which alternately turn the two output transistors on and off.

appdiag_sllsef3.gifFigure 39. SN6501-Q1 Block Diagram

The output frequency of the oscillator is divided down by an asynchronous divider that provides two complementary output signals, S and S, with a 50% duty cycle. A subsequent break-before-make logic inserts a dead-time between the high-pulses of the two signals. The resulting output signals, G1 and G2, present the gate-drive signals for the output transistors Q1 and Q2. As shown in Figure 40, before either one of the gates can assume logic high, there must be a short time period during which both signals are low and both transistors are high-impedance. This short period, known as break-before-make time, is required to avoid shorting out both ends of the primary.

op_sig_wf_llsea0.gifFigure 40. Detailed Output Signal Waveforms

9.2 Typical Application

typappnew_sllsef3.gifFigure 41. Typical Application Schematic (SN6501-Q1)

9.2.1 Design Requirements

For this design example, use the parameters listed in Table 1 as design parameters.

Table 1. Design Parameters

Input voltage range 3.3 V ± 3%
Output voltage 5 V
Maximum load current 100 mA

9.2.2 Detailed Design Procedure

The following recommendations on components selection focus on the design of an efficient push-pull converter with high current drive capability. Contrary to popular belief, the output voltage of the unregulated converter output drops significantly over a wide range in load current. The characteristic curve in Figure 11 for example shows that the difference between VOUT at minimum load and VOUT at maximum load exceeds a transceiver’s supply range. Therefore, in order to provide a stable, load independent supply while maintaining maximum possible efficiency the implementation of a low dropout regulator (LDO) is strongly advised.

The final converter circuit is shown in Figure 45. The measured VOUT and efficiency characteristics for the regulated and unregulated outputs are shown in Figure 1 to Figure 28. SN6501 Drive Capability

The SN6501 transformer driver is designed for low-power push-pull converters with input and output voltages in the range of 3 V to 5.5 V. While converter designs with higher output voltages are possible, care must be taken that higher turns ratios don’t lead to primary currents that exceed the SN6501 specified current limits. LDO Selection

The minimum requirements for a suitable low dropout regulator are:

  • Its current drive capability should slightly exceed the specified load current of the application to prevent the LDO from dropping out of regulation. Therefore for a load current of 100 mA, choose a 100 mA to 150 mA LDO. While regulators with higher drive capabilities are acceptable, they also usually possess higher dropout voltages that will reduce overall converter efficiency.
  • The internal dropout voltage, VDO, at the specified load current should be as low as possible to maintain efficiency. For a low-cost 150 mA LDO, a VDO of 150 mV at 100 mA is common. Be aware however, that this lower value is usually specified at room temperature and can increase by a factor of 2 over temperature, which in turn will raise the required minimum input voltage.
  • The required minimum input voltage preventing the regulator from dropping out of line regulation is given with:
  • Equation 1. VI-min = VDO-max + VO-max

    This means in order to determine VI for worst-case condition, the user must take the maximum values for VDO and VO specified in the LDO data sheet for rated output current (i.e., 100 mA) and add them together. Also specify that the output voltage of the push-pull rectifier at the specified load current is equal or higher than VI-min. If it is not, the LDO will lose line-regulation and any variations at the input will pass straight through to the output. Hence below VI-min the output voltage will follow the input and the regulator behaves like a simple conductor.

  • The maximum regulator input voltage must be higher than the rectifier output under no-load. Under this condition there is no secondary current reflected back to the primary, thus making the voltage drop across RDS-on negligible and allowing the entire converter input voltage to drop across the primary. At this point the secondary reaches its maximum voltage of
  • Equation 2. VS-max = VIN-max × n

with VIN-max as the maximum converter input voltage and n as the transformer turns ratio. Thus to prevent the LDO from damage the maximum regulator input voltage must be higher than VS-max. Table 2 lists the maximum secondary voltages for various turns ratios commonly applied in push-pull converters with 100 mA output drive.

Table 2. Required Maximum LDO Input Voltages for Various Push-Pull Configurations

3.3 VIN to 3.3 VOUT 3.6 1.5 ± 3% 5.6 6 to 10
3.3 VIN to 5 VOUT 3.6 2.2 ± 3% 8.2 10
5 VIN to 5 VOUT 5.5 1.5 ± 3% 8.5 10 Diode Selection

A rectifier diode should always possess low-forward voltage to provide as much voltage to the converter output as possible. When used in high-frequency switching applications, such as the SN6501 however, the diode must also possess a short recovery time. Schottky diodes meet both requirements and are therefore strongly recommended in push-pull converter designs. A good choice for low-volt applications and ambient temperatures of up to 85°C is the low-cost Schottky rectifier MBR0520L with a typical forward voltage of 275 mV at 100-mA forward current. For higher output voltages such as ±10 V and above use the MBR0530 which provides a higher DC blocking voltage of 30 V.

Lab measurements have shown that at temperatures higher than 100°C the leakage currents of the above Schottky diodes increase significantly. This can cause thermal runaway leading to the collapse of the rectifier output voltage. Therefore, for ambient temperatures higher than 85°C use low-leakage Schottky diodes, such as RB168M-40.

diode_forward_llsea0.gifFigure 42. Diode Forward Characteristics for MBR0520L (Left) and MBR0530 (Right) Capacitor Selection

The capacitors in the converter circuit in Figure 45 are multi-layer ceramic chip (MLCC) capacitors.

As with all high speed CMOS ICs, the SN6501 requires a bypass capacitor in the range of 10 nF to 100 nF.

The input bulk capacitor at the center-tap of the primary supports large currents into the primary during the fast switching transients. For minimum ripple make this capacitor 1 μF to 10 μF. In a 2-layer PCB design with a dedicated ground plane, place this capacitor close to the primary center-tap to minimize trace inductance. In a 4-layer board design with low-inductance reference planes for ground and VIN, the capacitor can be placed at the supply entrance of the board. To ensure low-inductance paths use two vias in parallel for each connection to a reference plane or to the primary center-tap.

The bulk capacitor at the rectifier output smoothes the output voltage. Make this capacitor 1 μF to 10 μF.

The small capacitor at the regulator input is not necessarily required. However, good analog design practice suggests, using a small value of 47 nF to 100 nF improves the regulator’s transient response and noise rejection.

The LDO output capacitor buffers the regulated output for the subsequent isolator and transceiver circuitry. The choice of output capacitor depends on the LDO stability requirements specified in the data sheet. However, in most cases, a low-ESR ceramic capacitor in the range of 4.7 μF to 10 μF will satisfy these requirements. Transformer Selection V-t Product Calculation

To prevent a transformer from saturation its V-t product must be greater than the maximum V-t product applied by the SN6501. The maximum voltage delivered by the SN6501 is the nominal converter input plus 10%. The maximum time this voltage is applied to the primary is half the period of the lowest frequency at the specified input voltage. Therefore, the transformer’s minimum V-t product is determined through:

Equation 3. EQ1_Vtmin_llsea0.gif

Inserting the numeric values from the data sheet into the equation above yields the minimum V-t products of

Equation 4. EQ2_Vtmin_llsea0.gif

Common V-t values for low-power center-tapped transformers range from 22 Vμs to 150 Vμs with typical footprints of 10 mm x 12 mm. However, transformers specifically designed for PCMCIA applications provide as little as 11 Vμs and come with a significantly reduced footprint of 6 mm x 6 mm only.

While Vt-wise all of these transformers can be driven by the SN6501, other important factors such as isolation voltage, transformer wattage, and turns ratio must be considered before making the final decision. Turns Ratio Estimate

Assume the rectifier diodes and linear regulator has been selected. Also, it has been determined that the transformer choosen must have a V-t product of at least 11 Vμs. However, before searching the manufacturer websites for a suitable transformer, the user still needs to know its minimum turns ratio that allows the push-pull converter to operate flawlessly over the specified current and temperature range. This minimum transformation ratio is expressed through the ratio of minimum secondary to minimum primary voltage multiplied by a correction factor that takes the transformer’s typical efficiency of 97% into account:

Equation 5. VP-min = VIN-min - VDS-max

VS-min must be large enough to allow for a maximum voltage drop, VF-max, across the rectifier diode and still provide sufficient input voltage for the regulator to remain in regulation. From the LDO SELECTION section, this minimum input voltage is known and by adding VF-max gives the minimum secondary voltage with:

Equation 6. VS-min = VF-max + VDO-max + VO-max
turns_ratio_llsea0.gifFigure 43. Establishing the Required Minimum Turns Ratio Through Nmin = 1.031 × VS-min / VP-min

Then calculating the available minimum primary voltage, VP-min, involves subtracting the maximum possible drain-source voltage of the SN6501, VDS-max, from the minimum converter input voltage VIN-min:

Equation 7. VP-min = VIN-min – VDS-max

VDS-max however, is the product of the maximum RDS(on) and ID values for a given supply specified in the SN6501 data sheet:

Equation 8. VDS-max = RDS-max × IDmax

Then inserting Equation 8 into Equation 7 yields:

Equation 9. VP-min = VIN-min - RDS-max x IDmax

and inserting Equation 9 and Equation 6 into Equation 5 provides the minimum turns ration with:

Equation 10. EQ8_amin_llsea0.gif


For a 3.3 VIN to 5 VOUT converter using the rectifier diode MBR0520L and the 5 V LDO TPS76350, the data sheet values taken for a load current of 100 mA and a maximum temperature of 85°C are VF-max = 0.2 V,
VDO-max = 0.2 V, and VO-max = 5.175 V.

Then assuming that the converter input voltage is taken from a 3.3 V controller supply with a maximum ±2% accuracy makes VIN-min = 3.234 V. Finally the maximum values for drain-source resistance and drain current at 3.3 V are taken from the SN6501 data sheet with RDS-max = 3 Ω and ID-max = 150 mA.

Inserting the values above into Equation 10 yields a minimum turns ratio of:

Equation 11. EQ9_amin_llsea0.gif

Most commercially available transformers for 3-to-5 V push-pull converters offer turns ratios between 2.0 and 2.3 with a common tolerance of ±3%. Recommended Transformers

Depending on the application, use the minimum configuration in Figure 44 or standard configuration in Figure 45.

Figure 44. Unregulated Output for Low-Current Loads With Wide Supply Range
Figure 45. Regulated Output for Stable Supplies and High Current Loads

The Wurth Electronics Midcom isolation transformers in Table 3 are optimized designs for the SN6501, providing high efficiency and small form factor at low-cost.

The 1:1.1 and 1:1.7 turns-ratios are designed for logic applications with wide supply rails and low load currents. These applications operate without LDO, thus achieving further cost-reduction.

Table 3. Recommended Isolation Transformers Optimized for SN6501

V x T
Application LDO Figures Order No. Manufacturer
1:1.1 ±2% 7 2500 6.73 x 10.05 x 4.19 3.3 V → 3.3 V No Figure 1
Figure 2
760390011 Wurth Electronics/ Midcom
1:1.1 ±2% 11 5 V → 5 V Figure 3
Figure 4
1:1.7 ±2% 3.3 V → 5 V Figure 5
Figure 6
1:1.3 ±2% 3.3 V → 3.3 V
5 V → 5 V
Yes Figure 7
Figure 8
Figure 9
Figure 10
1:2.1 ±2% 3.3 V → 5 V Figure 11
Figure 12
1.23:1 ±2% 5 V → 3.3 V Figure 13
Figure 14
1:1.1 ±2% 11 5000 9.14 x 12.7 x 7.37 3.3 V → 3.3 V No Figure 15Figure 16 750313734
1:1.1 ±2% 5 V → 5 V Figure 17
Figure 18
1:1.7 ±2% 3.3 V → 5 V Figure 19
Figure 20
1:1.3 ±2% 3.3 V → 3.3 V
5 V → 5 V
Yes Figure 21
Figure 22
Figure 23
Figure 24
1:2.1 ±2% 3.3 V → 5 V Figure 25
Figure 26
1.3:1 ±2% 5 V → 3.3 V Figure 27
Figure 28

9.2.3 Application Curve

See Table 3 for application curves.

9.2.4 Higher Output Voltage Designs

The SN6501 can drive push-pull converters that provide high output voltages of up to 30 V, or bipolar outputs of up to ±15 V. Using commercially available center-tapped transformers, with their rather low turns ratios of 0.8 to 5, requires different rectifier topologies to achieve high output voltages. Figure 46 to Figure 49 show some of these topologies together with their respective open-circuit output voltages.

Figure 46. Bridge Rectifier With Center-Tapped Secondary Enables Bipolar Outputs
Figure 48. Half-Wave Rectifier Without Center-Tapped Secondary Performs Voltage Doubling, Centered Ground Provides Bipolar Outputs
Figure 47. Bridge Rectifier Without Center-Tapped Secondary Performs Voltage Doubling
Figure 49. Half-Wave Rectifier Without Centered Ground and Center-Tapped Secondary Performs Voltage Doubling Twice, Hence Quadrupling VIN

9.2.5 Application Circuits

The following application circuits are shown for a 3.3 V input supply commonly taken from the local, regulated micro-controller supply. For 5 V input voltages requiring different turn ratios refer to the transformer manufacturers and their websites listed in Table 4.

Table 4. Transformer Manufacturers

Coilcraft Inc. http://www.coilcraft.com
Halo-Electronics Inc. http://www.haloelectronics.com
Murata Power Solutions http://www.murata-ps.com
Wurth Electronics Midcom Inc http://www.midcom-inc.com

Certain components might not possess AEC-Q100 Q1 qualification. For more detailed information on qualified components for automotive applications please refer to the automotive web page: http://www.ti.com/lsds/ti/apps/automotive/applications.page.

apcirc_sllsea0.gifFigure 50. Isolated RS-485 Interface
apcirc2_sllsea0.gifFigure 51. Isolated Can Interface
apcirc3_sllsea0.gifFigure 52. Isolated RS-232 Interface
apcirc4_sllsea0.gifFigure 53. Isolated Digital Input Module
apcirc5_sllsea0.gifFigure 54. Isolated SPI Interface for an Analog Input Module With 16 Inputs
apcirc6_sllsea0.gifFigure 55. Isolated I2C Interface for an Analog Data Acquisition System With 4 Inputs and 4 Outputs
apcirc7_sllsea0.gifFigure 56. Isolated 4-20 mA Current Loop