ZHCS987C June 2012 – September 2017
PRODUCTION DATA.
NOTE
Information in the following applications sections is not part of the TI component specification, and TI does not warrant its accuracy or completeness. TI’s customers are responsible for determining suitability of components for their purposes. Customers should validate and test their design implementation to confirm system functionality.
The suggested connections of the BCM excitation and sense electrodes to the device pins are shown in Figure 12. The circuit shows an electrical model of the body impedance being measured (RBODY) along with models for the electrode contact impedances. The components connecting the electrodes to the IOUTx and VSENSEx pins are meant to be replicated in the path of the calibration impedances as well. Suggestions for the component values are shown in Table 4.
The phase margin of the excitation amplifier can degrade if there is high capacitance at the input and output terminals. High capacitances can result can result from the capacitances from the electrodes, from protection diodes (for instance, ESD diodes), as well as the capacitance presented by the human body. Degradation of phase margin resulting from high capacitances can result in oscillations leading to reduced measurement accuracy. One way to improve the phase margin of the excitation amplifier is to introduce a series R-C at the output of the excitation amplifier in every measurement. This process is done using the components RCM = 1 kΩ and CCM = 1 nF in the simplistic model shown in Figure 13. This illustration is for a case where IOUT0 and IOUT1 are switched to the input and output of the excitation amplifier, respectively.
Such a scheme can be implemented in one of two methods:
Method 2 is preferable because this method involves only one RCM and one CCM.
The DAC frequency generator (DDS) is initialized on the register update of the DAC frequency register. The IQ demod clock divider is updated on the divider register value. Because the registers are written through the SPI interface (that is, asynchronous to the device clock), every time either of these registers are written, the phase relation between the DAC output and the I-Q demod clock can get altered. This alteration in phase relation can cause the phase of the I-Q measurement to be non-deterministic.
Two ways of circumventing this issue are:
A typical application of the AFE4300 is a weight scale, as shown in Figure 14, that includes a weight measurement as well as a body impedance measurement with the architecture.
The weight applied on a load-cell generates the differential voltage that is converted by the weight scale signal chain of the AFE. For the body impedance measurement, a sinusoidal current (most commonly at a frequency of 50 kHz) is injected into a pair of electrodes that make contact with the human body. Two more electrodes serve as sense electrodes and the differential voltage developed across the sense electrodes is measured and digitized by the AFE. The whole system is clocked using an external clock source.
Table 5 shows the typical requirements of a weight scale design using the AFE.
A body impedance measurement is usually performed using four electrodes: a pair of excitation electrodes and a pair of sense electrodes. Body contact to each electrode involves a series impedance resulting from the skin-electrode interface. On the excitation side, this contact impedances come in series with the body impedance and cause the voltage swing on the excitation terminals of the AFE to increase. Excessive contact impedances on the excitation electrodes can therefore cause the excitation amplifier to saturate even while measuring normal ranges of body impedance. On the sense electrodes, the input impedance of the receiver is 50 kΩ. As a result, the contact impedances on the sense electrodes cause a small attenuation in the effective signal input to the receiver. For these reasons, the ac contact impedance at the excitation frequency must be minimized on both the excitation and sense electrodes.
To deduce an accurate impedance value from the AFE output in the body impedance measurement requires calibration relative to known impedances. Calibration is usually performed by measuring two or more known impedances and by constructing a piece-wise linear curve between the AFE output and the impedance.
To conserve power when not used, the AFE can be put in a sleep mode in which all signal chains are powered down. This mode reduces the average power consumption significantly. When the user issues a power-up interrupt (pressing a button or so forth) to the system, the AFE can be programmed to come out of sleep mode, perform the measurement, and go back to sleep again. To account for drifts with time, TI recommends that calibration be done every time the AFE is woken up. For the BCM measurement, TI recommends measuring the calibration impedances before every fresh measurement of body impedance. For the weight scale measurement, TI recommends measuring the channel offset (the AFE output without any load) before the measurement of the load. Also after every wake-up, provide sufficient time for the signal chain to settle before doing any measurements.
To meet product-level ESD requirements, additional external ESD protection diodes may need to be used to protect the AFE pins that interface with the electrodes.
Figure 15 shows the linearity of the BCM up to 2.5 kΩ. As seen the figure, the maximum impedance that can be measured for the default configuration using the AFE4300 is typically 2.5 kΩ. However for better performance, TI suggests limiting the impedance to 1175 Ω. If higher impedance must be measured, the excitation current can be reduced by placing an external resistor of 1.5 kΩ (between DACOUT and DAC_FILT_IN), which increases the range by roughly 2x.