ZHCSJO8 May 2019 OPA818

ADVANCE INFORMATION for pre-production products; subject to change without notice.

Designs that require high bandwidth from a large area detector with relatively high transimpedance gain benefit from the low input voltage noise of the OPA818. This input voltage noise is peaked up over frequency by the diode source capacitance, and can, in many cases, become the limiting factor to input sensitivity. Figure 14 shows the transimpedance circuit with the parameters as defined in *Design Requirements*. To use the Microsoft Excel™ calculator available at *What You Need To Know About Transimpedance Amplifiers – Part 1* to help with the component selection, total input capacitance, C_{TOT},needs to be determined. C_{TOT} is referred as C_{IN} in the calculator. C_{TOT} is the sum of C_{D}, C_{DIFF}, and C_{CM} which is 7.4 pF. Using this value of C_{TOT}, and the targeted closed-loop bandwidth (f_{–3dB}) of 24 MHz and transimpedance gain of 100 kΩ results in a need for an amplifier with approximately 2.68 GHz GBWP and a feedback capacitance (C_{F}) of 0.092 pF as shown in Figure 15. These results are for a Butterworth response with a Q = 0.707 and a phase margin of approximately 65° which corresponds to 4.3% overshoot.

With OPA818's 2.7 GHz GBWP, it will be a suitable amplifier for the design requirements. A challenge with the calculated component results is practically realizing a 0.092 pF capacitor. Such a small capacitor can be realized by using a capacitive tee network formed by C_{1}, C_{2}, and C_{T} such as that shown in Figure 14. The equivalent capacitance, C_{EQ}, of the tee network is given by Equation 2.

Equation 2.

The tee network forms a capacitive attenuator from input to output with C_{1} and C_{T}, and from output to input with C_{2} and C_{T}. With the value of C_{T} being higher than C_{1} or C_{2}, only a fraction of the output signal is seen by C_{1}. This results in a much smaller shunting current provided to the input through C_{1} and this reduced shunting current effect is equivalent to how a much smaller capacitor behaves (at a fixed frequency, smaller capacitor has higher impedance and thus reduced current). It is recommended to keep the same level of attenuation from input to output and vice versa. To find the appropriate capacitor values for the tee network, chose an arbitrarily low but practically realizable and equal values for capacitors C_{1} and C_{2}, set C_{EQ} = C_{TOT}, and use Equation 3 to get the value of the tunable capacitor, C_{T}. The values of capacitors C_{1}, C_{2}, and C_{T} in Figure 14 were determined using this process.

Equation 3.

Figure 16 shows the TINA simulated closed-loop bandwidth response of the circuit in Figure 14. The circuit was designed for f_{–3dB} = 24 MHz and the simulated closed-loop 3-dB frequency is 24.6 MHz with about 0.1 dB peaking. The OPA818 TINA model models the input common-mode and differential capacitors so they should not be added externally when simulating in TINA. The noise simulation of the TIA circuit is shown in Figure 17. The output referred voltage noise is shown on the Y-axis to the left and the input referred current noise, which is essentially output referred voltage noise divided by the transimpedance gain of 100k, is shown on the secondary Y-axis to the right. The simulation results are fairly accurate because the OPA818 TINA model closely models the voltage and current noise performance of the amplifier. The flat-band output voltage noise is 41 nV/√Hz that is equivalent to 0.41 pA/√Hz of input referred current noise. The noise in relatively low frequency region where the noise gain of the amplifier is 1 V/V is dominated by the thermal noise of the 100 kΩ resistor (40.7 nV/√Hz at 27°C). At mid frequencies beyond the zero formed by R_{F} and C_{TOT}, the noise gain of the amplifier amplifies the voltage noise of the amplifier. The amplifier's noise starts to become the dominant noise contributor from this frequency onwards before the output noise starts to roll off at frequencies beyond the 3-dB closed-loop bandwidth. When looked at integrated root-mean-square (RMS) noise, the mid-frequency noise will be a significant contributor and hence using a 2.2 nV/√Hz low-noise amplifier like OPA818 is advantageous to minimize total RMS noise in the system.